Push-pull modulation system



Feb. 25, 1947. E. LABIN E'rAl.' 2,416,329

Y PUSH PULL MODULATION SYSTEM v F'iledAug. 24, v1942 2 Sheets-Sheet l (1R55 AMPLIFIER l @4g- 2. @ga

Patented Feb. 25, 1947 PUSH-PULL MoDULATIoN SYSTEM Emile Labin, New York, and Donald D. Grieg, Forest Hills, N. Y., assignors to Federal Tele-4 phone and Radio Corporation, a corporation of Delaware Application August 24, 1942, Serial No. 455,897

26 Claims.

The present invention relates to pulse generation and more lparticularly to systems for generating time modulated pulses for use in com-` munication systems and for other uses.

Several types of systems have been proposed for effecting communication by transmitting a number of pulses of current, the exact times of transmission of such pulses being controlled in accordance With the speech or otherintelligence to be transmitted. In some cases the pulses of current are themselves transmitted to a distance over wires, but in other cases they are used to modulate carriers so as to produce brief wave trains generally referred to as carrier pulses. Such systems of communication have been described in U. S. Patents 2,266,401, 2,256,336, 2,- 265,337, 2,262,838, and in copending U. S. applications 386,282 and 425,108, respectively, led on April 1, 1941, by E. Labin, and on December 31, 1941, by E. M. Deloraine and E. Labin, as Well as in a large number of other foreign patents and applications. In accordance with vthe systems heretofore proposed, the generation of time modulated pulses Was effected either by means of special vacuum tubes having cam-like target or masking means cut to a predetermined shape,

-or by providing multivibrator arrangements controlled by resistance/condenser time constants and capable of being influenced by the modulating signals so as to vary the vibrator rate.

It is an object of the present invention to provide a simpler, more reliable, and more economical method of generating time modulated pulses.

More particularly, it is an object to provide a system for generating time modulated pulses by the use of ordinary types of circuit components without requiring specially designed tubes.

It is a further obje-ct to provide such a system for vgenerating time modulated pulses which shall be capable of being stabilized by a master source of fixed waves, such as a sine wave oscillator or a stable unmodulated relaxation oscillator.

More particularly, it is an object to provide such a system wherein the time of the generated pulses is controlled by a fixed unmodulated wave.

Other objects of the invention will readily appear to those skilled in the art from the following detailed description of the invention, taken together with the annexed drawings, in which:

Fig. l is a schematic diagram of a time' modulation transmitter embodying one form` of our invention, and making use of electronic diode rectiers for performingr a full Wave rectiiying function. v I

Fig. 2 represents a modied form of rectifying circuit which may be substituted for the rectifying circuit of Fig. 1 and which effects modulation in a simpler but less symmetric fashion and employs dry rectifiers in place of f electronic diodes for performing the full wave rectification;

Fig. 3 represents a further form of rectifying circuit similar to thatY of Fig. 1 making use ofv triodes in place of diodes for .performing the full wave rectifier action. Y

Fig. 4 represents a circuit arrangement-Which may be substituted for the sine wave source shown in Fig. 1 and which is adapted to deliver triangular Waves insteadof sine waves Fig. 5a. represents a shaping circuit arrangement whichis used with the several circuits of Figures l, 2, 3, 4.

Fig. 5b represents an alternative type of shaping circuit utilizing double differentiation which may be substituted for that of Fig. 5a.

Fig. 6 is a set of curves useful in describing the operation of the invention.

Referring more particularly to Fig. l, III is a sine Wave source of good frequency stab-ilityhaving a frequency of the order of several kilocycles. For speech of the usual quality this would be of the order of 10 kc. The sine wave output from this source is delivered through an amplifier Hu and, if desired, through another amplifier II2 (which may be more or less limiting action for a purpose later to be described) to the full wave rectifying circuiti I3. This .circuitr as shown es.

sentally comprises two wave transmission means such as diodes Nos.v II4 and II5 of the ordinary hot cathode electronic type, an input transformer l I6 and an output resistor II'I. In many cases it is desirableto provide a condenser IIS across the secondary of the Vtransformer H6 to tune this approximately to the 10 kc. sine Wave input former vI2I being inserted between the two Wind-- ings. The. modulating transformer IZIhas also a split secondary in order. to allow the insertion of battery I2I', which serves to bias the diodes H4 and I I5 in opposite sense so as to unbalance therectiiier. The, modulating signal applied to thistransformer I2I may be speech from a source I22;`r The symmetrical disposition of transformersY III andIZI allows the eiiects of the D. C. currents in these transformersv to be canceled out. The output of circuit -I.I3 is applied to a limiter and shaping amplifier which delivers time modulated pulsesof the type describediin copending-U. S. application 386,282.y The output from the shaping circuit |23 isthen applied to modulate an R.F.- amplier |24 which is Vex- I cited from a suitable R.F. source |25 and whose output is radiated over an antenna |26..`

The operationof the systemof Fig. 1 can best be understood from 'the following detailed explanation'taken in conjunction with theurves 3 of Fig. 6 and the diagram of Fig. 1. The sine waves applied between the plates of diodes IIe and H are represented by curve A of Fig. 6 in relation to the various thresholds of rectiiication which mayeXist for different values of the speech input signal potential. Assuming, first, for simplicity that the speech source is delivering its maximum negative potential via transformer I2! and assuming that such potential is just equal and opposite to the potentialk oflbattery EZI so that the resultant potential difference across each half of the secondary of transformer IZI'with respect to ground is zero, it will then be clear that the plates of the diodes Ill?. and IE5 will swing symmetricallyabove and below ground potential. y

Since the resistor II1 is returned to ground, and since the diode currents inrthis resistance cancel out, ground potential is the threshold level above which each of the rectifiers begin to pass current and therefore the threshold a represented by a dot dash line in Fig. 6 is shown as symmetrically disposed with respect to the input sine wave A. Under such conditions the output from rectifier H4 will have the formvshown in curve'Ba and the output from rectiiier H5 will have the exactly similar form shown in curve Ca. The combined Voutput current flowing through resistor III will have the form shown in curve Da being thus a simple half wave rectifying sine wave having a number ci sharp cusps :12, y, .e equally spaced in time.

If we consider conditions at an oppositeV eX- treme of the speech voltage when the potential delivered through transformer IZI is again equal to the potential of battery I2i but is in the same sense so as to aid the battery potential, it will thenbe clear that under such conditions the plate of diode H will be several volts positive with respect to groundwhile that'of diode II5 will be a corresponding number of Volts negative with respect to ground. Under. such conditions current will tend to flow through-diode IIeX- cept through the most negative portions 'of the sine wave input and therefore the current output from this diodewilllbe of the form shown in curve Bc. Conversely, the diode I I5 willby its negative bias be prevented from carrying current except during the brief intervals when the lower end of transformer II6 is strongly rpositive and thus the output current from this diode will have the form shown in curve Cc in Fig. 6. Thus the combined output fromboth diodes flowing through receiver II'I will have theform shown inY curve Dc consisting'of alternately'large andy small peaks with the cusps az, y", s unequally spaced. l v f Y A Because of the symmetrical manner of 4applying the biasing potentials in circuit I lait willvbe noticed'that as one rectiflerlpasses more than half a cycle theother passescorrespondinglylessthan half a cycle of the input wave and 'therefore'one may consider that the efect'of the'modulation is to shift the rectiiication threshold which in the absence of bias would be as shown at .a with respect to the sinejwave A, tothe asymmetric position shown in c. If curve A be taken as representing the wave applied tothe primary oi f ltransformer i i5, then the `region above any given threshold representsv the portion of the cycle whichis passed by the upper rectiiier YI IfiqwhileA the region below a threshold represents that portion of Vthe cycle passedV by rectifier I I 51 -During the time whenV the speech signal has its maximum negative value (so that the total bias due to transformer battery I2I is zero) the eiective threshold will be threshold a. I During the opposite extreme as explained, the threshold c will be eiective.

For Zero values of the input speech signal the bias of the full wave rectifier will have an intermediate value and the threshold b will be effective. Under such zero signal conditions the output from rectifier 6I@ will correspond to those portions oi curve A above the threshold b, being thus of the form shown in curve Bb While output from rectier H5 Will correspond to those portions of curve A below this threshold b, being thus of the form shown in curve Cb. The combined output during zero signal intervals will. be of the form Vshown in curve Db consisting of a number of peaks (or troughs) whose amplitudes differ and whose cusps x', y', e are correspondingly unequally spaced in time.

The various cusps y, e or r', y', z orV z", y, e are thus time modulated i. e. the time intervals :ry and ya are respectively reduced to x"y and `increased to y"e or vice versa, corresponding to the amplitude of the modulating signal applied through the transformer I2 i.'

Fig. 2' represents another simpler form of full wave rectifying circuit which may be substituted for circuit M3 of Fig. l. This arrangement ls essentiaily'similar to circuitl I I3 except that the audio-input transformer 22| does not require a' split-secondary winding and the battery 22|' need not be center tapped. The two rectiers 2I d and 255 are represented as dry rectifiers in the circuit of Fig. 2 rather than being electronic diodes as in circuit H3. It will be understood, however, that diodes can be used in the circuit ofY Fig. 2 or dry rectiers can be used in the circuit of Fig. l, as may be desired. Y

rihe simplification of the circuit of Fig. 2 is effected by arranging the modulating and biasing potentials from transformer 22| and battery 221| in asymmetric fashion so that only the upper rectifier 2id receives the biasing and modulating potentials, while the other rectiiienZIE is returned directly to ground. The operation ofV ci Fig. G. The output from rectier 2I5 is un-Y altered by the modulation and always has the form of part of the curve F consisting of a series of semi sine waves spaced one cycle apart. But the current iow in diodeY 2i54 is stopped at the various instants p, q, r or p', q', r or p", q, r depending lupon the value of additional bias on rectifier Zi due to the'drop in resistance 211 produced by the variable current ilowing through the rectiiier Zit plus the 'modulatingV bias; This variable current depends upon the modulation as shown of curves Ea, El), Fc. During the moment When the modulating signal .has its `maximum negative value we may Yassume'that this signal just cancels the biasing voltagek of battery 2'2I so that the net bias of rectifier 2 I4 is zero. Under such conditionsthe output from this rectifier 2H! Will consist of a series of half sineiwaves as shown in curve Ea. DuringV theropposite polarity of theV rEc which starts at the instants p, q, r. During intermediate conditions when'the speech signal has zero value the positive bias onrectiiier II4 will be just equal to the voltage ofbattery I2I' and the corresponding output will be only slightly greater than a half sine wave having the form of curve Eb of Fig. 6 starting at the instants p', q', r. The combined output from the two rectiers will, during intervals of maximum negative signal, consist of a combination of curves Ea and F, being thus a simple full wave rectified sine wave with equally spaced cusps at times p, q, r. During the intervals of maximum positive speech signal, on the other hand, the combined output in resistor I I'I of Fig. 2 will be a combination of the curves Ec and F, the cusps taking place at the instants p', q', 1".

It will be noted that simultaneously with the displacement of the cusps a corresponding variation in amplitude takes place, as shown by the subsequent positions p, p', p". In order to obtain identical pulses modulated vin time only, it is necessary to provide a variable clipping level in the subsequent shaping stage, in the opposite sense to the amplitude variations. It is one of the purposes of the shaping circuits of Figs. 5a and 5b described in the following to provide this compensating bias.

Fig. 3 illustrates still another form of circuit, making use of triodes in place of diodes for effecting the full wave rectifying action. The input transformer 3 I 6 serves in this circuit not only for applying the kc. foundation wave to the rectifying elements 3I4 and 3I5 but also for applying the modulating bias thereto. For this purpose the transformer has in addition to its main primary winding 34| an auxiliary split primary consisting of windings342 and 343. The main primary winding 34| receives the 10 kc. input while the auxiliary primary 342--343 receives the speech modulating signal. Both pri- -maries are symmetrically coupled to the split-secondary so as to deliver both the foundation wave and the modulating signal in push-pull fashion to the triodes 3I4 and 3I5. It will be understood that these triodes do not actually act as true rectiers in the sense of a non-linear impedance for conducting current asymmetrically; rather they act as amplifiers to produce in the output a curve which is more or less proportional to the input over a certain range of input voltages and which is substantially unresponsive to variations inV input below such predetermined input voltage. The threshold at which such tubes become unresponsive to variations in input signal is the so-called cutoif point ordinarily corresponding to a few volts negative potential on the control grid.

The two biasing batteries 32V and 32!" have preferably such values that tube SI5 is about as far below cutoif as tube4 3I4 is above its cutoff point. The difference between these two batteries, moreover, is preferably such that when the audio modulating signal has its maximum negative value (thus rendering the grid of tube 3I4 more negative and that of 3I5 more positive) the grids will be at the same potential and will both be just at the cutoff point. Under such conditions the outputs from the tubes I4 and 3I5, respectively, will correspond to curves Ba and Ca of Fig. 6 and the combined output thereof in resistor 3H will correspond to curve Da.

When the speech signal has its maximum positive polarity, on the other hand, the 'difference in potential between the grids of the tubes is accentuated and the outputs of the tubes 3I4 and SI5 will correspond respectively to curves Bc and Cc, the combined output then corresponding to curve Dc. During intermediate conditions the intermey being derived from the same energy applied to the input.

Although it is preferred to employ sine waves as the foundation waves to be full wave rectified in accordance with the present invention, it is possible to attain useful results of the invention with other wave forms. A triangular zigzag wave form is especially suitable when linear time modulation is desired over a considerable range (i e., where it is desired that the pulses produced be displaced by a large fraction of the recurrence intervals and where it is desired that the deviation of each pulse from normal position should be directly proportional to the value of the input signal).

Fig. 4 illustrates a circuit suitable for producing such symmetrical triangular zigzag waves. As shown in Fig. 4, 4M Ais a square wave source which may, for example, comprise a multivibrator synchronized if desired from asinusoidal oscillator and clipped if necessary to render its output truly square. The output from such square wave source is applied to an integrating net work 402 which may be of any suitable type capable of reasonably accurately forming the integral of a waveform applied to its input circuit. The output of such integrating network 402 will be of the desired symmetric zigzag form; The circuit arrangement of Fig. 4 may be substituted for sine wave source III in Fig. 1 and may be usedwith cusping circuitV I I3 or with either of the cusping circuits of Fig. 2 or 3.

Fig. 5a illustrates one of the possible shaping circuit arrangements which has been designated so far by |23. This circuit .follows the rectifying circuits and transforms the input waves into pulses of substantially constant amplitude and width. Basically the circuit of Fig. 5a comprises an arrangement for passing only the most positive tips of any signal applied to it. Such an arrangement for passing only the most positive peaks may comprise almost any form of detector working on the grid leak principle. In the form shown the circuit comprises a pentode 502 having its control grid fed via the RC combination of condenser 503 and grid leak 564 which determines the biasing potential on its grid. It shouldbe noted that when the symmetrical circuit of II3 is utilized, l

condenser 503 and resistor 504 may be omitted and the output of circuit II3 connected directly to the grid. The output circuit of such pentode includes the load resistor 506 and the'outputcoupling condenser 501, as well as plate and Vscreen Preferably the biasing batteries 508 and 509. screen battery (and possibly also the plate battery) is of lower than normal potential so that the grid base (i. e., the voltage separation between the cutoff threshold and the grid current threshold) is only a very few volts.

The operation of the circuit of Fig. 5a when connected to the output of the cusping circuit I I 3 is as follows: The output of circuit II3 is in the form of a series of negative rounded peaks with sharp positive cusps therebetween. The position of such wave with respect to the zero axis will sia-isses naturally'aline itself to c cntainrno D. C. component because ofthe presence Aof the coupling condenser 563 of Fig. 5.

The grid leakll `will tend torender the control grid of tube 502 more and more negative when any substantial grid current is being drawn. Thusthis grid will automatically adjust itself to the point where only the very tips of the positive cusps drive the grids sufficiently positive to draw grid current. Because of the adjustment of the tube to have a comparatively narrow grid base the resultv will be that only a small portion of l each curve immediately adjacent the'cusps will be passed by the pentode 5M since the rest of the curve will lie below the cutoff threshold.4 As a result the output through resistor 535 will consist of a, number of narrow peaked waves corre sponding to the cusps of 'the output wave fromy the circuit H3. These peaked waves may be further shaped, of course, by the inclusion of an additional clipping amplifier provided at the out put of pentode 502.

When the circuit of Fig. 5a, is used in conjunction with the unsymmetrical type of circuit of Fig. 2, proper adjustment of the RC combination 503,'` 504 permits elimination of the variations in amplitude of the cusps as described previously. This action takes place due to the compensating gridcurrent ow. For any particularcusp an plitude a given amount of grid .current will Viiow through the grid leak 5M. For a rcater or smaller cusp amplitude the amount of grid currentilow will berespectively greater or smaller. leak 504 in combination with the coupling condenser 593 which determines the speed degree of compensation will thus develop a yariable negative biasing potential in step with the This biasing po.- l

Variations in cusp amplitude. tential is applied to the grid of tube 5M providing the variable clipping level indicated .on Fig. 6 by C1, C2, C3. v

Fig. 5b indicates an alternate method of shaping. The output of circuit I i3 is applied `through a double differentiation circuit 5i! which may comprise two differentiation circuits of any amplification between them. Thus two RC circuits 5il are shown in Fig. 5b followed by the amplifying pentode 5i2. Alternately inductance types of differentiation networks or a' combination of RC and L networks may be readily substituted. Y

The circuits of Fig. r5a and Fig. 5b are possible forms of circuit l23whether the circuit H3 be i employed orwhether the substituted circuits or Figs. 2 and 3 are used. The combination at present believed to be preferable corresponds to Fig. l1 with the modified circuits of 5a substituted therein. The other combinations, however, are equally effective.

Although it is preferred to effect the timemodi ulation as above described by varying-.the relative position lof the foundation wave with respectito the thresholds of discontinuity of one or both halves of the full Wavevrectifier, very satisfacv tory results can also berobtained by giving vthe full wave rectifying means a fixed unbalance and applied foundation wave. For this purpose a jack |29 may be provided on the amplifier i i@ so that plug |21 to speech source 22 may, lif desired, be unplugged from clipping circuit M3 `and plugged into this amplifier IIB. Underi such The grid i Iin Dit

known type connected in tandem with or without j conditions the bias battery I2I' of circuit H3 will maintain the diode I ifi positive and the diode H5 negative by a small amount depending upon the amplitude of the waves transmitted from amplifier Hi? through amplifier H2. This fixed bias will represent a greater or smaller fraction of the total sine wavev amplitude and therefore the degree to which the cusps are unevenlyspaced will vary with the amplitude of the sine wave from amplier im. Such an arrangement is ordinarily not as desirable as the previously described types yof modulation wherein one of, or both the full wave rectifier biasesY are altered (or where construing the action from another viewpoint the input wave isv superposed upon a D. C. bias so as to shift it in position without Varying with its A. C. amplitude),` Very satisfactory results, however, can be obtained even when the speech source is plugged into, jack i23 instead of jack f2.3.

Although .certain embodimentsof our invention have been shown and described for purposes of illustration, lit will be clear that many modifications, additions and omissions may be made within the scope and spirit thereof, as definen` in the appended claims.

What is claimed is:V

A time modulation system comprising a source ofy fixed frequency foundation waves, full wave rectifier means connected to effectively full wave rectify said foundation waves whereby rectified waves having sharpY cusps arev produced, for unbaiancing said rectier means with res" ect ,to Vsaid foundation waves by a percentage of the ampitude of said waves, a source of signal waves, means for varying said imbalance percentage under control of said signal waves where the spacing of said cusps is varied, and means f Jr deriving from said rectified waves a. series of pulses which correspond in time to said cusps.

2. A system according to claim l, wherein said foundation waves are fixed in amplitude and wherein said means for varying said unbalance vpercentage comprises means for varying the abthe amplitude of said foundation waves.

A time modulation system comprising a source of xed frequency foundation waves, full wave rectifier means connected to eifectively full wave rectify said foundation waves whereby rectified waves having sharp cuspsare produced, a source of signal waves' representing intelligence to be transmitted, means for unbalancing said rectifier means under vcontrol of said signal waves whereby the spacing of said cusps is varied, and means for deriving from said rectiedwaves a series of pulses which correspond in time to said cusps. l

A time modulation system comprising a source of xed frequency substantially sinusoidal foundation waves, full wave rectiiier means aconnested to effectively full wave rectify said foundation waves whereby rectified waves vhaving sharp cusps are produced, a source-of signal waves representing speech to be transmitted, `means Vfor unbaiancing said r ctifier means Vto a variable degree under control of` said signal Ywaves whereby the spacing of said cusps varied, and means for deriving from-said rectified Waves a series of narrow pulses which correspond in time to said cusps.

6. A time modulation system comprising a source of fixed frequency foundation waves, a first wave transmission means having a first discontinuity threshold and connected to transmit those portions of said foundation waves which lie on a given side of said first threshold, a second wave transmission means having a second discontinuity threshold and connected to transmit those portions of said foundation waves which lie on a given side of said second threshold, means for combining the wave portions transmitted by said first and second transmission means, whereby a combined wave having sharp cusps is produced, a source of signal waves, means for varying at least one of said discontinuity thresholds under control of said signal waves whereby the time intervals between the cusps of said combined wave are varied, and means for deriving from said combined wave a series of pulses which correspond in time to said cusps.

'1. A system according to claim 6, wherein said first and second wave transmission means are rectiers.

8. A system according to claim 6, wherein said first and second wave transmission means are electronic diode rectiers.

9. A system according to claim 1, wherein said means for deriving a series of pulses from said rectified waves comprise means for transmitting only the tips of the cusps of said rectified waves.

10. A time modulation system comprising a source of fixed frequency foundation waves, first and secondwave transmission means, each of said transmission means having a threshold clipping level for passing energy according to those portions of waves applied thereto which extend beyond the threshold level thereof, means to apply a foundation wave from said source to the first and second transmission means in push-pull relation so that said first transmission means responds to those wave portions extending beyond the threshold level thereof in one polarity direction and said second transmission means responds to those wave portions extending beyond the threshold level thereof in the opposite polarity direction, means for combining the wave portions transmitted by said first and said 'second transmission means whereby a combined wave having sharp cusps is produced, a source of signal energy, and means responsive to said signal energy for controlling the threshold clipping operation of the foundation Wave, whereby the timing of said cusps is modulated according to said signal energy.

11. A system according to claim wherein the means for controlling the threshold clipping operation includes means for varying the threshold level of one of said transmission means.

l2. A system according to claim 10 wherein the means for controlling the threshold clipping operation includes means for varying simultaneously the threshold clipping levels of both said first and said second transmission means.

13. A system according to claim 10 wherein the means for controlling the threshold clipping operation includes means for maintaining fixed the threshold clipping levels of both said transmission means at levels different from the axis level of said foundation wave and means for varying the amplitude of the foundation wave according to said signal wave.

14. A system according to claim 10 in combination with means for deriving from said combined wave a series of pulses corresponding in time to said cusps.

15. A system according to claim 10 wherein said first and said second transmission means are rectifiers.

16. A system according to claim 10 wherein said first and said second transmission means are electronic diode rectifiers.

1'7. A system according to claim 10 wherein said first and said second wave transmission means comprise grid controlled vacuum tubes with the means for applying the foundation waves being connected in push-pull relation to the control grids thereof.

18. A system according to claim 10 wherein said rst and said second wave transmission means are dry rectiers.

19. A method of producing time modulated signals comprising producing a fixed frequency foundation wave, passing energy according to those portions of the foundation wave which extend in one polarity direction beyond a first threshold level, passing energy according to those portions of the foundation wave which extend in the opposite polarity direction beyond a second threshold level, combining the energy thus passed to produce a combined wave having sharp cusps, and controlling the relationshipfbetween said threshold levels and the amplitude of the foundation wave according to a signal wave so that the time intervals between the cusps of said combined wave vary in accordance with said signal wave.

20. A method according to claim 19 wherein the controlling operation includes varying one of the threshold levels in accordance with the signal wave.

21. A method according to claim 19 wherein said first and second clipping levels are maintained in a fixed displaced relation with respect to the axis of the foundation Wave, and the controlling operation includes varying the amplitude of the foundation wave in accordance with the signal wave.

22. A method according to claim 19 wherein the controlling operation includes varying simultaneously and in opposite polarity directions the said rst and said second threshold levels in accordance with the signal wave.

23. A method according to claim 19 in combination with the step of threshold clipping the cusp portions of the combined wave thereby deriving a series of narrow width pulses corresponding in time to said cusps.

24. A method according to claim 19 wherein the step of producing the foundation wave includes producing said Wave in sinusoidal form.

25. A method according to claim 19 wherein the step of producing the foundation wave includes producing said wave in zig-zag form.

26. A method according to claim 19 wherein the controlling operation includes varying the threshold levels in accordance with the signal wave.

EMILE LABIN. DONALD D. GRIEG.

REFERENCES CITED Name Date Barnard Sept. 24, 1940 Number 

